Basic Engineering Circuit Analysis [10 ed.] 0470633220, 9780470633229

Table of contents :
Cover
Title Page
Copyright
Brief Contents
Contents
Preface
CHAPTER 1 BASIC CONCEPTS
1.1 System of Units
1.2 Basic Quantities
1.3 Circuit Elements
Summary
Problems
CHAPTER 2 RESISTIVE CIRCUITS
2.1 Ohm’s Law
2.2 Kirchhoff’s Laws
2.3 Single-Loop Circuits
2.4 Single-Node-Pair Circuits
2.5 Series and Parallel Resistor Combinations
2.6 Circuits with Series-Parallel Combinations of Resistors
2.7 Wye (omitted) Delta Transformations
2.8 Circuits with Dependent Sources
2.9 Resistor Technologies for Electronic Manufacturing
2.10 Application Examples
2.11 Design Examples
Summary
Problems
CHAPTER 3 NODAL AND LOOP ANALYSIS TECHNIQUES
3.1 Nodal Analysis
3.2 Loop Analysis
3.3 Application Example
3.4 Design Example
Summary
Problems
CHAPTER 4 OPERATIONAL AMPLIFIERS
4.1 Introduction
4.2 Op-Amp Models
4.3 Fundamental Op-Amp Circuits
4.4 Comparators
4.5 Application Examples
4.6 Design Examples
Summary
Problems
CHAPTER 5 ADDITIONAL ANALYSIS TECHNIQUES
5.1 Introduction
5.2 Superposition
5.3 Thévenin’s and Norton’s Theorems
5.4 Maximum Power Transfer
5.5 Application Example
5.6 Design Examples
Summary
Problems
CHAPTER 6 CAPACITANCE AND INDUCTANCE
6.1 Capacitors
6.2 Inductors
6.3 Capacitor and Inductor Combinations
6.4 RC Operational Amplifier Circuits
6.5 Application Examples
6.6 Design Examples
Summary
Problems
CHAPTER 7 FIRST- AND SECOND-ORDER TRANSIENT CIRCUITS
7.1 Introduction
7.2 First-Order Circuits
7.3 Second-Order Circuits
7.4 Application Examples
7.5 Design Examples
Summary
Problems
CHAPTER 8 AC STEADY-STATE ANALYSIS
8.1 Sinusoids
8.2 Sinusoidal and Complex Forcing Functions
8.3 Phasors
8.4 Phasor Relationships for Circuit Elements
8.5 Impedance and Admittance
8.6 Phasor Diagrams
8.7 Basic Analysis Using Kirchhoff’s Laws
8.8 Analysis Techniques
8.9 Application Examples
8.10 Design Examples
Summary
Problems
CHAPTER 9 STEADY-STATE POWER ANALYSIS
9.1 Instantaneous Power
9.2 Average Power
9.3 Maximum Average Power Transfer
9.4 Effective or rms Values
9.5 The Power Factor
9.6 Complex Power
9.7 Power Factor Correction
9.8 Single-Phase Three-Wire Circuits
9.9 Safety Considerations
9.10 Application Examples
9.11 Design Examples
Summary
Problems
CHAPTER 10 MAGNETICALLY COUPLED NETWORKS
10.1 Mutual Inductance
10.2 Energy Analysis
10.3 The Ideal Transformer
10.4 Safety Considerations
10.5 Application Examples
10.6 Design Examples
Summary
Problems
CHAPTER 11 POLYPHASE CIRCUITS
11.1 Three-Phase Circuits
11.2 Three-Phase Connections
11.3 Source/Load Connections
11.4 Power Relationships
11.5 Power Factor Correction
11.6 Application Examples
11.7 Design Examples
Summary
Problems
CHAPTER 12 VARIABLE-FREQUENCY NETWORK PERFORMANCE
12.1 Variable Frequency-Response Analysis
12.2 Sinusoidal Frequency Analysis
12.3 Resonant Circuits
12.4 Scaling
12.5 Filter Networks
12.6 Application Examples
12.7 Design Examples
Summary
Problems
CHAPER 13 THE LAPLACE TRANSFORM
13.1 Definition
13.2 Two Important Singularity Functions
13.3 Transform Pairs
13.4 Properties of the Transform
13.5 Performing the Inverse Transform
13.6 Convolution Integral
13.7 Initial-Value and Final-Value Theorems
13.8 Application Examples
Summary
Problems
CHAPTER 14 APPLICATION OF THE LAPLACE TRANSFORM TO CIRCUIT ANALYSIS
14.1 Laplace Circuit Solutions
14.2 Circuit Element Models
14.3 Analysis Techniques
14.4 Transfer Function
14.5 Pole-Zero Plot/Bode Plot Connection
14.6 Steady-State Response
14.7 Application Example
14.8 Design Examples
Summary
Problems
CHAPTER 15 FOURIER ANALYSIS TECHNIQUES
15.1 Fourier Series
15.2 Fourier Transform
15.3 Application Examples
15.4 Design Example
Summary
Problems
CHAPTER 16 TWO-PORT NETWORKS
16.1 Admittance Parameters
16.2 Impedance Parameters
16.3 Hybrid Parameters
16.4 Transmission Parameters
16.5 Parameter Conversions
16.6 Interconnection of Two-Ports
16.7 Application Examples
16.8 Design Example
Summary
Problems
APPENDIX: COMPLEX NUMBERS
Index

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$//7+(+(/35(6285&(6$1'3(5621$/6833257 0 2. Poles or zeros at the origin of the form j; that is, (j)+N for zeros and (j)-N for poles 3. Poles or zeros of the form (1 + j) 4. Quadratic poles or zeros of the form 1 + 2(j) + (j)2 Taking the logarithm of the magnitude of the function H(j) in Eq. (12.7) yields 20 log 10∑H(j)∑ = 20 log 10 K0 ; 20N log 10∑j∑ + 20 log 10 @1 + j1 @

+ 20 log 10 @1 + 23 Aj3 B + Aj3 B @ 2

12.8

+ p - 20 log 10 @1 + ja @

2 - 20 log 10 @1 + 2b Ajb B + Ajb B @ p

Note that we have used the fact that the log of the product of two or more terms is equal to the sum of the logs of the individual terms, the log of the quotient of two terms is equal to the difference of the logs of the individual terms, and log 10 An = n log 10 A. The phase angle for H(j) is

/ H(j) = 0 ; N(90°) + tan-1 1 + tan-1 a

23 3 1 - 223

b

2b b p + p - tan-1 a - tan-1 a b 1 - 22b

12.9

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VA R I A B L E - F R E Q U E N C Y N E T W O R K P E R F O R M A N C E

Magnitude characteristic

Figure 12.10 Log magnitude gain (dB)

Phase characteristic

0.1

1.0

10

0

100

 (rad/s:log scale) (a)

Log magnitude gain (dB)

Magnitude characteristic with slope of –20N dB/decade

0

Phase characteristic

–N(90°)

1.0  (rad/s:log scale) (b)

Log magnitude gain (dB)

Magnitude and phase characteristics for a constant term and poles and zeros at the origin.

20 log10K0

Phase (deg)

CHAPTER 12

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Phase (deg)

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Phase characteristic Magnitude characteristic with slope of ±20N dB/decade 1.0  (rad/s:log scale)

±N(90°) Phase (deg)

irwin12_577-666hr.qxd

(c)

As Eqs. (12.8) and (12.9) indicate, we will simply plot each factor individually on a common graph and then sum them algebraically to obtain the total characteristic. Let us examine some of the individual terms and illustrate an efficient manner in which to plot them on the Bode diagram. Constant Term The term 20 log 10 K0 represents a constant magnitude with zero phase shift, as shown in Fig. 12.10a. Poles or Zeros at the Origin Poles or zeros at the origin are of the form (j);N, where + is used for a zero and-is used for a pole. The magnitude of this function is ;20N log 10 , which is a straight line on semilog paper with a slope of ;20N dB兾decade; that is, the value will change by 20N each time the frequency is multiplied by 10, and the phase of this function is a constant ;N(90°). The magnitude and phase characteristics for poles and zeros at the origin are shown in Figs. 12.10b and c, respectively. Simple Pole or Zero Linear approximations can be employed when a simple pole or zero of the form (1 + j) is present in the network function. For  V 1, (1 + j) L 1, and therefore, 20 log 10∑(1 + j)∑ = 20 log 10 1 = 0 dB. Similarly, if  W 1, then (1 + j) L j, and hence 20 log 10∑(1 + j)∑ L 20 log 10 . Therefore, for  V 1 the response is 0 dB and for  W 1 the response has a slope that is the same as that of a simple pole or zero at the origin. The intersection of these two asymptotes, one for  V 1 and one for  W 1, is the point where  = 1 or  = 1兾, which is called the break frequency. At this break frequency, where  = 1兾, 20 log 10 @(1 + j1)@ = 20 log 10(2)1兾2 = 3 dB. Therefore, the actual curve deviates from the asymptotes by 3 dB at the break frequency. It can be shown that at

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SECTION 12.2

Magnitude (dB)

1

2

3

4 5 6 7 8 91

3 4 5 6 7 8910



–45°/decade

–40

–45°

–60

–12

–80 –90°

–18 –20 0.2

0.5

1.0

2.0

10

4.0

 (rad/s)(Log scale) (a)

90°

=tan–1

±12



60 45°

±6

dB ±45°/decade

±20 dB/decade

30

Phase shift (deg)

Magnitude (dB)

±18 dB=20 log10|(1+j)|

0 0

0.1

0.2

0.5

1.0

2.0

4.0

589

Figure 12.11

dB=20 log10|(1+j)–1| 0 = tan–1 dB –20 dB/decade –20

0

–6

2

S I N U S O I D A L F R E Q U E N C Y A N A LY S I S

Phase shift (deg)

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10

 (rad/s)(Log scale) (b)

one-half and twice the break frequency, the deviations are 1 dB. The phase angle associated with a simple pole or zero is  = tan-1 , which is a simple arctangent curve. Therefore, the phase shift is 45° at the break frequency and 26.6° and 63.4° at one-half and twice the break frequency, respectively. The actual magnitude curve for a pole of this form is shown in Fig. 12.11a. For a zero the magnitude curve and the asymptote for  W 1 have a positive slope, and the phase curve extends from 0° to +90°, as shown in Fig. 12.11b. If multiple poles or zeros of the form (1 + j)N are present, then the slope of the high-frequency asymptote is multiplied by N, the deviation between the actual curve and the asymptote at the break frequency is 3N dB, and the phase curve extends from 0 to N(90°) and is N(45°) at the break frequency. Quadratic Poles or Zeros Quadratic poles or zeros are of the form 1 + 2 (j) + (j)2 This term is a function not only of  but also of the dimensionless term , which is called the damping ratio. If >1 or  = 1, the roots are real and unequal or real and equal, respectively, and these two cases have already been addressed. If Q Q Q21, the poles represented by the quadratic factor in the denominator will simply roll off the fre-

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SECTION 12.4

SCALING

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quency response, as illustrated in Fig. 12.12a, and at high frequencies the slope of the composite characteristic will be –20 dB/decade. If 0